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EE210 Digital Electronics Class Lecture 2 March 27, 2008

EE210 Digital Electronics Class Lecture 2 March 27, 2008. Introduction to Electronics. 2. 1.4.6 Amp Power Supplies. Power supplied to Load by Amp is Greater than Power Drawn from Input Signal To supply that extra power the Amp Need DC Power Supplies for their Operation

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EE210 Digital Electronics Class Lecture 2 March 27, 2008

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  1. EE210Digital ElectronicsClass Lecture 2March 27, 2008

  2. Introduction to Electronics 2

  3. 1.4.6 Amp Power Supplies • Power supplied to Load by Amp is Greater than Power Drawn from Input Signal • To supply that extra power the Amp Need DC Power Supplies for their Operation • In addition the DC PS supply power that might be Dissipated in Internal Amp Ckt

  4. Power Deliverd to Amp Pdc = V1I1 + V2I2 Amp Power-balance Eq. Pdc+ PI = PL + Pdissipated

  5. Amp Efficiency η ≡ (PL / Pdc) x 100 • What about PIandPdissipated ?? • Power Efficiency is Important Performance Parameter for Amps that Handle Large Amounts of Power … • … and Such Power Amplifiers are Used as Output Amps of Stereo Systems

  6. Simple Ckt Diagram – We shall adopt the convention illustrated and will not Explicitly show connections of Amp to DC PS

  7. Example 1.1 (Page 17) Data Given; V1=V2= 10V I1 = I2 = 9.5 mA vI = 1 V, vO = 9V RL = 1kΩ iI = 0.1 mA Find: Av, Ai, Ap,Pdc, Pdissipated, η

  8. 1.4.7 Amp Saturation • Practically Amp Transfer Characteristics Only Remain Linear for Limited Range of I/O Voltages • Amp Operated from 2 PS the Output Voltage can not exceed specified positive limit and can not decrease below specified negative limit

  9. An Amplifier Transfer Characteristic. vI Must be kept within Linear Range of Operation.

  10. 1.4.8 Nonlinear TC and Biasing • Except from output Saturation Effect the Amp TC have been assumed linear • In Practical Amps the TC may exhibit nonlinearities of various magnitudes • Biasing is a Simple Technique to Obtain Linear Amplification From Amp Having Nonlinear TC

  11. Considerable Nonlinear Amp TC. Ampis Biased to Obtain Linear Operation and the Signal Amplitude is Kept Small

  12. Time-varying Signal to be Amplified is Superimposed on the DC Bias VI and Total Instantaneous Input vI(t) = VI + vi(t) • And vO(t) = VO + vo(t) • With vo(t) = Av vi(t) • Where Av = dvO / dvI |at Q is the Slope of Almost Linear Segment of TC • This Way Linear Amplification is Achieved with a Limitation of Keeping Input Signal Sufficiently Small

  13. Example 1.2 (Page 21) Example 1.2 Transfer Characteristic of Amplifier. Note That Amplifier is Inverting (Negative Gain)

  14. 1.4.9 Symbol Convention Terminology and Symbol Convention to be Used • Instantaneous Quantities Lower Case Symbol with Uppercase Sub iA(t), vC(t) • DC Quantities Upper Case Symbol Uppercase Sub IA, VC • PS (dc) Voltages Uppercase V with Double-letter Uppercase Sub, VDDSimilar notation for Current from PS • Incremental Signal Quantities Lowercase Symbol with Lowercase Sub ia(t), vc(t) • Sine Wave Signal Amplitude Uppercase Letter with Lowercase Sub Ia, Vc

  15. Symbol Convention Employed

  16. 1.7 Digital Logic Inverters • Logic Inverter is a Most Basic Element in Digital Ckt Design • Plays a Role Parallel to the Amp in analog Ckt • We will get Introduced to Logic Inverter in This Section

  17. 1.7.1 Function of the Inverters • Logic Inverter INVERTS the Logic Value of its Input Signal • That is for 0 input, out put will be 1, and vice versa In Voltage Level Terms When vIis Low (close to 0) the vO will be high VDD

  18. 1.7.2 The Voltage Transfer Characteristic • VTC to Quantify Operation of Inverter • Observe the TC of Amplifier in Ex 1.2 This Inverting Amp can be used as Inverter when we use its Extreme Regions of Operation – Opposite to Amp Dig App Make Use of Gross nonlinearity exhibited by VTC

  19. VTC of an inverter. VOH Does Not Depend on Exact Value of vIaslong as vI≤ VIL. When vI> VILInverter inAmp mode or Transition Region. VIL is Max Value That vI Can Have While Being Interpreted by Inverter as Representing Logic 0. VOLDoes Not Depend on Exact Value of vIaslong as vI≥ VIH. VIH is Min Value That vI Can Have While Being Interpreted by Inverter as Representing Logic 1.

  20. 1.7.3 Noise Margins • Insensitivity of Inverter Output to Exact Value of vI within allowed regions is great advantage over analog ckts. • To Quantify Insensitivity Consider One Inverter Driving Similar Inverter • Noise Margin for High Input NMH = VOH – VIH • Noise Margin for Low Input NML = VIL - VOL

  21. Four Parameters VOH,VIH,VIL, and VOL Define VTC of Inverter and Determine its Noise Margin, Which in Turn Measures its Ability to Tolerate Input Signal Variations • VOL: Output Low Level • VOH: Output High Level • VIL: Max Input as Logic 0 • VIH: Min Input as Logic 1 • NML: Noise Margin for Low Input = VIL - VOL • NMH: Noise Margin for High Input = VOH – VIH

  22. 1.7.4 The Ideal VTC • What Makes an Ideal VTC for Inverter? • Ideal VTC Maximizes the Noise margins and Distributes Them Equally B/W the Low and High Regions • VOH is at Max Possible Value VDD • VOL is at Min possible Value 0 V

  23. The Ideal VTC (Cont…) • VILand VIH are equal at Mid of (VDD/2) • Width of Transition Region (Imp for Amp) is Zero • Steep Transition at Threshold Voltage (VDD/2) – Gain infinite • Noise Margins are Equal NMH = NML = VDD/2 • CMOS Inverter Has Close to Ideal VTC

  24. 1.7.5 Inverter Implementation Implemented using Transistors Operating as Voltage Controlled Switches

  25. Transistor Switches are NOT Perfect • Their OFF Resistance is High, But • ON Resistance is not Zero and Some BJTs Exhibit Offset Voltage as well • The Result is That When vIis High VOL Is not Ideally Zero

  26. More Elaborate Implementation Exists Utilizing Pair of Complementary Switches (CMOS Based). When I/P Low, VOH = VDD, No Current FlowsWhen I/P High, Ron Connect Ground, VOL = 0

  27. Implementation Using Double-Throw Switch (ECL Chap 7 & 11) • Steer IEE into one of two resistors Connected to +ve PS VCC • Connected to RC1 Logic Inversion-function at vO1 • Output Voltage is Independent of Switch Resistance

  28. 1.7.6 Power Dissipation • Digital Systems use large number of Logic Gates • Space and Economy Require as Few IC as Possible • Hence, As Many Logic gates As Possible on IC Chip • In Present VLSI 100K+ gates on IC • To Keep Acceptable limit of Power Dissipation in Chip, Power Dissipation/Gate Must be Minimum • Power Dissipation is Very Important Performance Measure of Logic Inverter

  29. When vI Low no Power Dissipated • In other State Dissipation is V2DD/R and is Substantial • This Dissipation Occurs even When Inverter not Switching -- Static Power Dissipation

  30. This Inverter Exhibit No Static Power Dissipation • BUT …

  31. There is Always A component of Power Dissipation Due to Capacitance • Cap Exists between Output Node of Inverter and Ground • Internal Cap of Switches • Wires Connecting Output to Other Ckts have Cap • Input Cap of Any CKt Driven by Inverter

  32. When Inverter is Switching from One State to Another, Current must Flow thru Switches to Charge and Discharge the Load Capacitance • The Current Give Rise to dissipation Called Dynamic Power Dissipation (Chap 4)

  33. 1.7.7 Propagation Delay • Inverters are Characterized in Terms of The Time Delay Between Switching of vI (Low to High) and Corresponding Change Appearing at the Output • 2 Reasons for Propagation Delay: • Transistors (Switches) Exhibit Finite (nonzero) Switching Time • The Cap needs to Charge/Discharge before Output Change • To Analyze Inverter Switching Need to Understand Time Response of Single-Time-Constant Ckts (STC) [Appendix D]

  34. Step Function Applied to an STC Network with Time Constant τ, Out putat any time: y(t) = Y∞ - ( Y∞ - Y0+)e-t/τ Y∞is final value where response is heading Y0+value of response immediately after t=0 • Output at any time t is difference between final value and gap whose initial value is Y∞ - Y0+and shrinking exponentially

  35. Example 1.6 Before t=0 vI is high, and VOL is = Voffset + V in Ron At t=0 SW opens, V across Cap cannot change instantaneously, therefore at t=0+ O/P is still 0.55. Cap charges thru R and vO rises exponentially toward VDD

  36. Using vO(∞) = 5 V and vO(0+) = 0.55V in Eq. y(t) = Y∞ - ( Y∞ - Y0+ )e -t/τ vO(t) = 5 – (5 – 0.55) e-t/τ τ = RC. To find tPLH vO(tPLH) = 0.5(5+0.55) tPLH = 0.69τ = 0.69RC = 0.69x1000x10-11 = 6.9 ns

  37. Formal Definitions of Propagation Delay of Inverter. I/P with Finite Rise and Fall Time is applied, Inverted O/P Exhibits Finite Rise and Fall times. There is also delay time between I/P and O/P waveforms. Usually Prop. Delay is Specified by the average of hi-lo Prop. and lo-hi Prop. and measured at 50% of I/P and O/P waveforms.

  38. HW #1 • Problems at the end of Chapter 1: Prob. 1.30 Prob. 1.35 Prob. 1.36 Prob. 1.86 Due Next Week: 3 April 2008

  39. In Next Class We Will Discuss: Chap 3 Diodes Topics: 3.1 The Ideal Diode 3.7 Physical Operation of Diodes 3.9 The SPICE Diode Model and Simulation Examples

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