Active clamp circuits

1. Active clamp circuits • Can be viewed as a lossless voltage-clamp snubber that employs a current-bidirectional switch • See Vinciarelli patent (1982) for use in forward converter • Related to other half-bridge ZVS circuits • Can be added to the transistor in any PWM converter • Not only adds ZVS to forward converter, but also resets transformer better, leading to better transistor utilization than conventional reset circuit

2. The conventional forward converter • Max vds = 2Vg + ringing • Limited to D < 0.5 • On-state transistor current is P/DVg • Magnetizing current must operate in DCM • Peak transistor voltage occurs during transformer reset • Could reset the transformer with less voltage if interval 3 were reduced

3. The active-clamp forward converter • Better transistor/transformer utilization • ZVS • Not limited to D < 0.5 Transistors are driven in usual half-bridge manner:

4. Approximate analysis:ignore resonant transitions, dead times, and resonant elements

5. Charge balance Vb can be viewed as a flyback converter output. By use of a current-bidirectional switch, there is no DCM, and LM operates in CCM.

6. Peak transistor voltage Max vds = Vg + Vb = Vg /D’ which is less than the conventional value of 2 Vg when D < 0.5 This can be used to considerable advantage in practical applications where there is a specified range of Vg

7. Design example • 270 V ≤ Vg ≤ 350 V • max Pload = P = 200 W • Compare designs using conventional 1:1 reset winding and using active clamp circuit

8. Conventional case Peak vds = 2Vg + ringing = 700 V + ringing Let’s let max D = 0.5 (at Vg = 270 V), which is optimistic Then min D (at Vg = 350 V) is(0.5)(270)/(350) = 0.3857 The on-state transistor current, neglecting ripple, is given by ig  = DnI = Did-on with P = 200 W = Vg  ig  = DVg id-on So id-on = P/DVg = (200W) / (0.5)(270 V) = 1.5 A

9. Active clamp case:scenario #1 • Suppose we choose the same turns ratio as in the conventional design. Then the converter operates with the same range of duty cycles, and the on-state transistor current is the same. But the transistor voltage is equal to Vg /D’, and is reduced: • At Vg = 270 V: D = 0.5 peak vds = 540 V • At Vg = 350 V: D = 0.3857 peak vds = 570 V • which is considerably less than 700 V

10. Active clamp case:scenario #2 • Suppose we operate at a higher duty cycle, say, D = 0.5 at Vg = 350 V. Then the transistor voltage is equal to Vg /D’, and is similar to the conventional design under worst-case conditions: • At Vg = 270 V: D = 0.648 peak vds = 767 V • At Vg = 350 V: D = 0.5 peak vds = 700 V • But we can use a lower turns ratio that leads to lower reflected current in Q1: • id-on = P/DVg = (200W) / (0.5)(350 V) = 1.15 A

11. Active clamp circuits: some examples Basic switch network reduces to: (if the blocking capacitor is an ac short circuit, then we obtain alternately switching transistors—original MOSFET plus the auxiliary transistor, in parallel. The tank L and C ring only during the resonant transitions)

12. Example: addition of active clamp circuit to the boost converter The upper transistor, capacitor Cb, and tank inductor are added to the hard-switched PWM boost converter. Semiconductor output capacitances Cds are explicitly included in the basic operation.

13. Active clamp circuit on the primary sideof the flyback converter

14. Active clamp to snub the secondary-side diodes of the ZVT phase-shifted full bridge converter

15. Active clampforward converter

16. Waveforms(including Ll)

17. Details: different modes

19. About Ll